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EL5156, EL5157, EL5256, EL5257
Data Sheet July 2, 2004 FN7386.2
PRELIMINARY
<1mV Voltage Offset, 600MHz Amplifiers
The EL5156, EL5157, EL5256, and EL5257 are 600MHz bandwidth -3dB voltage mode feedback amplifiers with DC accuracy of <0.01%, 1mV offsets and 40kV/V open loop gains. These amplifiers are ideally suited for applications ranging from precision measurement instrumentation to high speed video and monitor applications demanding the very highest linearity at very high frequency. Capable of operating with as little as 6.0mA of current from a single supply ranging from 5V to 12V and dual supplies ranging from 2.5V to 5.0V these amplifiers are also well suited for handheld, portable and battery-powered equipment. With their capability to output as much as 140mA, member of this family is comfortable with demanding load conditions. Single amplifiers are available in SOT-23 packages and duals in a 10-pin MSOP package for applications where board space is critical. Additionally, singles and duals are available in the industry-standard 8-pin SO package. All parts operate over the industrial temperature range of -40C to +85C.
Features
* 600MHz -3dB bandwidth, 240MHz 0.1dB bandwidth * 700V/s slew rate * <1mV input offset * Very high open loop gains 92dB * Low supply current = 6mA * 140mA output current * Single supplies from 5V to 12V * Dual supplies from 2.5V to 5V * Fast disable on the EL5156 and EL5256 * Low cost
Applications
* Imaging * Instrumentation * Video * Communications devices
Ordering Information
PART NUMBER EL5156IS EL5156IS-T7 EL5156IS-T13 EL5157IW-T7 EL5157IW-T7A EL5256IY EL5256IY-T7 EL5256IY-T13 EL5257IS EL5257IS-T7 EL5257IS-T13 EL5257IY EL5257IY-T7 EL5257IY-T13 PACKAGE 8-Pin SO 8-Pin SO 8-Pin SO 5-Pin SOT-23 5-Pin SOT-23 10-Pin MSOP 10-Pin MSOP 10-Pin MSOP 8-Pin SO 8-Pin SO 8-Pin SO 8-Pin MSOP 8-Pin MSOP 8-Pin MSOP TAPE & REEL 7" 13" 7" (3K pcs) 7" (250 pcs) 7" 13" 7" 13" 7" 13" PKG. DWG. # MDP0027 MDP0027 MDP0027 MDP0038 MDP0038 MDP0043 MDP0043 MDP0043 MDP0027 MDP0027 MDP0027 MDP0043 MDP0043 MDP0043
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright (c) Intersil Americas Inc. 2004. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc. All other trademarks mentioned are the property of their respective owners.
EL5156, EL5157, EL5256, EL5257 Pinouts
EL5156 (8-PIN SO) TOP VIEW
NC 1 IN- 2 IN+ 3 VS- 4 + 8 CE 7 VS+ 6 OUT 5 NC OUT 1 VS- 2 IN+ 3 +4 IN-
EL5157 (5-PIN SOT-23) TOP VIEW
5 VS+
EL5256 (10-PIN MSOP) TOP VIEW
INA+ 1 CEA 2 VS- 3 CEB 4 INB+ 5 + + 10 INA9 OUTA 8 VS+ 7 OUTB 6 INBOUTA 1 INA- 2 INA+ 3 VS- 4
EL5257 (8-PIN SO) TOP VIEW
8 VS+ + + 7 OUTB 6 INB5 INB+
2
EL5156, EL5157, EL5256, EL5257
Absolute Maximum Ratings (TA = 25C)
Supply Voltage between VS and GND. . . . . . . . . . . . . . . . . . . 13.2V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA Pin Voltages . . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to VS +0.5V Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +125C Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65C to +150C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40C to +85C Current into IN+, IN-, CE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5mA
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER AC PERFORMANCE BW -3dB Bandwidth
VS+ = +5V, VS- = -5V, CE = +5V, RF = RG = 562, RL = 150, TA = 25C, unless otherwise specified. CONDITIONS MIN TYP MAX UNIT
DESCRIPTION
AV = +1, RL = 500, CL = 4.7pF AV = +2, RL = 150
600 180 210 70 500 640 700 15 0.005 0.04 12 5.5
MHz MHz MHz MHz V/s V/s ns % nV/Hz pA/Hz
GBWP BW1 SR
Gain Bandwidth Product 0.1dB Bandwidth Slew Rate
RL = 150 AV = +2 VO = -3.2V to +3.2V, AV = +2, RL = 150 VO = -3.2V to +3.2V, AV = +1, RL = 500
tS dG dP VN IN
0.1% Settling Time Differential Gain Error Differential Phase Error Input Referred Voltage Noise Input Referred Current Noise
AV = +1 AV = +2, RL = 150 AV = +2, RL = 150
DC PERFORMANCE VOS TCVOS AVOL Offset Voltage Input Offset Voltage Temperature Coefficient Open Loop Gain Measured from TMIN to TMAX VO is from -2.5V to 2.5V 10 -1 0.5 -3 40 1 mV V/C kV/V
INPUT CHARACTERISTICS CMIR CMRR IB Common Mode Input Range Common Mode Rejection Ratio Input Bias Current Guaranteed by CMRR test VCM = 2.5V to -2.5V EL5156 & EL5157 EL5256 & EL5257 IOS RIN CIN Input Offset Current Input Resistance Input Capacitance -2.5 80 -1 -600 -250 10 108 -0.4 -200 100 25 1 +1 +600 +250 +2.5 V dB A nA nA M pF
OUTPUT CHARACTERISTICS VOUT Output Voltage Swing RL = 150 to GND RL = 500 to GND IOUT Peak Output Current RL = 10 to GND 3.4 3.6 80 3.6 3.8 140 V V mA
ENABLE (EL5156 and EL5256 ONLY) tEN tDIS Enable Time Disable Time 200 300 ns ns
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EL5156, EL5157, EL5256, EL5257
Electrical Specifications
PARAMETER IIHCE IILCE VIHCE VILCE SUPPLY ISON ISOFF PSRR Supply Current - Enabled (per amplifier) No load, VIN = 0V, CE = +5V 5.1 5 75 6.0 13 90 6.9 25 mA A dB VS+ = +5V, VS- = -5V, CE = +5V, RF = RG = 562, RL = 150, TA = 25C, unless otherwise specified. CONDITIONS CE = VS+ CE = VS5 VS+ -1 VS+ -3 MIN TYP 0 13 MAX -1 25 UNIT A A V V
DESCRIPTION CE Pin Input High Current CE Pin Input Low Current CE Input High Voltage for Power-down CE Input Low Voltage for Power-up
Supply Current - Disabled (per amplifier) No load, VIN = 0V, CE = 5V Power Supply Rejection Ratio DC, VS = 3.0V to 6.0V
Typical Performance Curves
4 3 NORMALIZED GAIN (dB) 2 1 0 -1 -2 -3 -4 -5
RL=150 CL=4.7pF AV=+2 AV=+1 PHASE ()
135 90 45 0 -45 -90 -135 -180 -225 -270
RL=150 CL=4.7pF AV=+2
AV=+5 AV=+10
AV=+10 AV=+5
-6 100K
1M
10M FREQUENCY (Hz)
100M
1G
-315 100K
1M
10M FREQUENCY (Hz)
100M
1G
FIGURE 1. SMALL SIGNAL FREQUENCY RESPONSE - GAIN
FIGURE 2. SMALL SIGNAL FREQUENCY RESPONSE PHASE FOR VARIOUS GAINS
4 3 NORMALIZED GAIN (dB) 2 1 0 -1 -2 -3 -4 -5 -6 100K 1M 10M FREQUENCY (Hz) 100M 1G RL=150 RL=750 RL=50 VS=5V AV=+2 RF=RG=562
5 4 RL=500 GAIN (dB) 3 2 1 0 -1 -2 -3 -4
AV=+1 RL=500
CL=27pF CL=10pF CL=4.7pF
CL=1pF
-5 100K
1M
10M FREQUENCY (Hz)
100M
1G
FIGURE 3. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL
FIGURE 4. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL
4
EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued)
5 4 NORMALIZED GAIN (dB) 3 2 1 0 -1 -2 -3 -4
AV=+2 RL=500 RF=RG=500
16 22pF 10pF 8.2pF 4.7pF 0pF 14 12 10 GAIN (dB) 8 6 4 2 0 -2
AV=+2 RF=RG=562 RL=150
180pF 100pF 33pF
10pF 0pF
-5 100K
1M
10M FREQUENCY (Hz)
100M
1G
-4 100K
1M
10M FREQUENCY (Hz)
100M
1G
FIGURE 5. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL
FIGURE 6. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL
5 4 NORMALIZED GAIN (dB) 3 2 1 0 -1 -2 -3 -4
5 NORMALIZED GAIN (dB) AV=+5 RL=500 100pF 82pF 68pF 22pF 4 3 2 1 0 -1 -2 -3 -4 1M 10M FREQUENCY (Hz) 100M 1G 100K 1M 10M FREQUENCY (Hz) 100M 500M 3.0V 4.0V 5.0V 2.0V RL=500 CL=4.7pF AV=+1
-5 100K
FIGURE 7. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL
FIGURE 8. FREQUENCY RESPONSE vs POWER SUPPLY
5 4 NORMALIZED GAIN (dB) 3 2 1 0 -1 -2 -3 -4 -5 100K AV=+2 AV=+1 RL=500 CL=4.7pF 1M AV=+5 10M 100M 1G NORMALIZED GAIN (dB) AV=+1
4 3 2 1 0 -1 -2 -3 -4 -5 -6 100K 1M 10M FREQUENCY (Hz) 100M 1G AV=-2 VS=5V RF=620 RL=150
AV=-1
FREQUENCY (Hz)
FIGURE 9. EL5256 SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS GAINS
FIGURE 10. SMALL SIGNAL INVERTING FREQUENCY RESPONSE FOR VARIOUS GAINS
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EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued)
4 3 NORMALIZED GAIN (dB) 2 1 0 -1 -2 -3 -4 -5
AV=+1 CL=0.2pF
5 4 NORMALIZED GAIN (dB) RL=500 RL=300 3 2 1 0 -1 -2 -3 -4
AV=+1 CL=4.7pF
500
RL=150
200 100 50
-6 100K
1M
10M FREQUENCY (Hz)
100M
1G
-5 100K
1M
10M FREQUENCY (Hz)
100M
1G
FIGURE 11. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL
FIGURE 12. EL5256 SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL
5 4 NORMALIZED GAIN (dB) 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M 100M 200M 0.2pF 0pF NORMALIZED GAIN (dB) AV=+2 RL=500 CL=4.7pF RF=500 12pF 8.2pF 4.7pF
4 3 2 1 0 -1 -2 -3 -4 -5
AV=+5 CL=4.7pF RL=500 RF=102
68pF 47pF
22pF 4.7pF 0pF
100K
1M
10M
100M 200M
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 13. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CIN
FIGURE 14. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CIN
4 3 NORMALIZED GAIN (dB) 2 1 0 -1 -2 -3 -4 -5 -6 100K 1M 10M FREQUENCY (Hz) 100M 1G 350 562 500 250 VS=5V AV=+2 RL=150 CL=4.7pF RF=RG=1k NORMALIZED GAIN
6 5 4 3 2 1 0 -1 -2 -3 -4 100K 1M 10M FREQUENCY (Hz) AV=+2 CL=4.7pF RL=500
RF=RG=3k 2k 1k 500 200
100M
1G
FIGURE 15. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RF AND RG
FIGURE 16. EL5256 SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RF/RG
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EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued)
5 NORMALIZED GAIN (dB) 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 15dBm 17dBm 20dBm 10M FREQUENCY (Hz) 100M 600M -20dBm 10dBm NORMALIZED GAIN (dB) AV=+2 RL=200 CL=4.7pF
5 4 3 2 1 0 -1 -2 -3 -4 -5 100K AV=+1 RL=500 CL=4.7pF 1M
CHANNEL #1 CHANNEL #2
10M
100M
1G
FREQUENCY (Hz)
FIGURE 17. LARGE SIGNAL FREQUENCY RESPONSE FOR VARIOUS INPUT AMPLITUDES
FIGURE 18. CHANNEL TO CHANNEL FREQUENCY RESPONSE
0 -10 CROSS TALK (10dB) -20 -30 -40 -50 -60 -70 -80 -90 -100 100K 1M 10M FREQUENCY (Hz) 100M 1G BW (MHz) AV=+5 RL=500 CL=4.7pF
700 600 500 400 300 200 100 0 4.5 5.5
AV=+1,RL=500, CL=5pF
AV=+1, RL=150
AV=+2,RL=150
6.5
7.5 8.5 VS (V)
9.5
10.5
11.5
FIGURE 19. EL5256 CROSS TALK vs FREQUENCY CHANNEL A TO B & B TO A
FIGURE 20. BANDWIDTH vs SUPPLY VOLTAGE
4 3 NORMALIZED GAIN (dB) 2 1 0 -1 -2 -3 -4 -5
VOLTAGE NOISE (nV/Hz), CURRENT NOISE (pA/Hz)
AV=+5 CL=4.7pF
1K
500 1000
100
VN 10 IN 1 10
100 50
-6 100K
1M
10M FREQUENCY (Hz)
100M
1G
100
1K
10K
100K
1M
10M
FREQUENCY (Hz)
FIGURE 21. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RL
FIGURE 22. VOLTAGE AND CURRENT NOISE vs FREQUENCY
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EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued)
-20 -30 -40 CMRR (dB) -50 -60 -70 -80 -90 -100 -110 100 1K 10K 100K 1M 10M 100M IMPEDANCE ()
1000 100 10 1 0.01 0.001
AV=+2 RL=0 RG=RF=400
1K
10K
100K
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 23. CMRR
FIGURE 24. OUTPUT IMPEDANCE
-10 DISABLED ISOLATION (dB) -20 -30 -40 -60 -70 -80 -90 -100 -50
VS=5V AV=+2 RL=150
6.1 6 5.9 IS (mA) 5.8 5.7 5.6 5.5 5.4
ISIS+
-110 100K
1M
10M FREQUENCY (Hz)
100M
1G
5.3 4.5 5 5.5 6 6.5 7 7.5 8 8.5 9 9.5 10 10.51111.5 12 VS (V)
FIGURE 25. INPUT TO OUTPUT ISOLATION vs FREQUENCY DISABLE
FIGURE 26. SUPPLY CURRENT vs SUPPLY VOLTAGE
0.8 AV=+2 RL=500 SUPPLY=5.0V 12.3mA 0.7 PEAKING (dB) 0.6 0.5 0.4 0.3 0.2 0.1 0 4.5 5.5 6.5 7.5 8.5 VS (V) 9.5 10.5 11.5 AV=+1 RL=500 CL=5pF
ENABLE 192ns
DISABLE 322ns
TIME (400ns/DIV)
FIGURE 27. ENABLE/DISABLE RESPONSE
FIGURE 28. PEAKING vs SUPPLY VOLTAGE
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EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued)
VOUT (40mV/DIV)
AV=+2 RL=500 SUPPLY=5.0V 12.3mA OUTPUT=200mVP-P VOUT (40mV/DIV)
0 RISE 20%-80% T=2.025ns
0
FALL 80%-20% T=1.91ns AV=+2 RL=500 SUPPLY=5.0V 12.3mA OUTPUT=200mVP-P TIME (4ns/DIV)
TIME (4ns/DIV)
FIGURE 29. SMALL SIGNAL RISE TIME
FIGURE 30. SMALL SIGNAL FALL TIME
VOUT (400mV/DIV)
VOUT (400mV/DIV)
AV=+2 RL=500 SUPPLY=5.0V 12.3mA OUTPUT=2.0VP-P
AV=+2 RL=500 SUPPLY=5.0V 12.3mA OUTPUT=2.0VP-P
0 RISE 20%-80% T=1.657ns
0
FALL 80%-20% T=1.7ns
TIME (2ns/DIV) TIME (2ns/DIV)
FIGURE 31. LARGE SIGNAL RISE TIME
FIGURE 32. LARGE SIGNAL FALL TIME
1.8 POWER DISSIPATION (W) 1.6 1.4
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD
1.2 POWER DISSIPATION (W) 1 0.8 0.6
JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD
1.2 1.136W 1 0.8 0.6 543mW 0.4 0.2 0 0 SOT23-5 JA=230C/W 25 50
781mW SO8 JA=160C/W
SO8 JA=110C/W
0.4 488mW 0.2 0 SOT23-5 JA=256C/W 0 25 50 75 85 100 125 150
75 85 100
125
150
AMBIENT TEMPERATURE (C)
AMBIENT TEMPERATURE (C)
FIGURE 33. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
FIGURE 34. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
9
EL5156, EL5157, EL5256, EL5257 Typical Performance Curves (Continued)
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD
1 0.9 POWER DISSIPATION (W) 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0
0.6 POWER DISSIPATION (W) 0.5
870mW MSOP8/10 JA=115C/W
486mW 0.4 0.3 0.2 0.1 0
MSOP8/10 JA=206C/W
0
25
50
75 85
100
125
0
25
50
75 85
100
125
AMBIENT TEMPERATURE (C)
AMBIENT TEMPERATURE (C)
FIGURE 35. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
FIGURE 36. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
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EL5156, EL5157, EL5256, EL5257 Product Description
The EL5156, EL5157, EL5256, and EL5257 are wide bandwidth, single or dual supply, low power and low offset voltage feedback operational amplifiers. Both amplifiers are internally compensated for closed loop gain of +1 or greater. Connected in voltage follower mode and driving a 500 load, the -3dB bandwidth is about 610MHz. Driving a 150 load and a gain of 2, the bandwidth is about 180MHz while maintaining a 600V/s slew rate. The EL5156 and EL5256 are available with a power down pin to reduce power to 17A typically while the amplifier is disabled. and 0.04%, while driving 150 at a gain of 2. Driving high impedance loads would give a similar or better dG and dP performance.
Driving Capacitive Loads and Cables
The EL5156 and EL5157 families can drive 27pF loads in parallel with 500 with less than 5dB of peaking at gain of +1. If less peaking is desired in applications, a small series resistor (usually between 5 to 50) can be placed in series with the output to eliminate most peaking. However, this will reduce the gain slightly. If the gain setting is greater than 1, the gain resistor RG can then be chosen to make up for any gain loss which may be created by the additional series resistor at the output. When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, a back-termination series resistor at the amplifier's output will isolate the amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. Again, a small series resistor at the output can help to reduce peaking.
Input, Output and Supply Voltage Range
The EL5156 and EL5157 families have been designed to operate with supply voltage from 5V to 12V. That means for single supply application, the supply voltage is from 5V to 12V. For split supplies application, the supply voltage is from 2.5V to 5V. The amplifiers have an input common mode voltage range from 1.5V above the negative supply (VS- pin) to 1.5V below the positive supply (VS+ pin). If the input signal is outside the above specified range, it will cause the output signal distorted. The outputs of the EL5156 and EL5157 families can swing from -4V to 4V for VS = 5V. As the load resistance becomes lower, the output swing is lower. If the load resistor is 500, the output swing is about -4V at a 4V supply. If the load resistor is 150, the output swing is from -3.5V to 3.5V.
Disable/Power-Down
The EL5156 and EL5256 can be disabled and their output placed in a high impedance state. The turn off time is about 330ns and the turn on time is about 130ns. When disabled, the amplifier's supply current is reduced to 17A typically, thereby effectively eliminating the power consumption. The amplifier's power down can be controlled by standard TTL or CMOS signal levels at the ENABLE pin. The applied logic signal is relative to VS- pin. Letting the ENABLE pin float or applying a signal that is less than 0.8V above VS- will enable the amplifier. The amplifier will be disabled when the signal at ENABLE pin is above VS+ -1.5V.
Choice of Feedback Resistor and Gain Bandwidth Product
For applications that require a gain of +1, no feedback resistor is required. Just short the output pin to the inverting input pin. For gains greater than +1, the feedback resistor forms a pole with the parasitic capacitance at the inverting input. As this pole becomes smaller, the amplifier's phase margin is reduced. This causes ringing in the time domain and peaking in the frequency domain. Therefore, RF can't be very big for optimum performance. If a large value of RF must be used, a small capacitor in the few Pico farad range in parallel with RF can help to reduce the ringing and peaking at the expense of reducing the bandwidth. For gain of +1, RF = 0 is optimum. For the gains other than +1, optimum response is obtained with RF between 500 to 750. The EL5156 and EL5157 families have a gain bandwidth product of 210MHz. For gains > = 5, its bandwidth can be predicted by the following equation: (Gain)X(BW) = 210MHz.
Output Drive Capability
The EL5156 and EL5157 families do not have internal short circuit protection circuitry. They have a typical short circuit current of 95mA and 70mA. If the output is shorted indefinitely, the power dissipation could easily overheat the die or the current could eventually compromise metal integrity. Maximum reliability is maintained if the output current never exceeds 40mA. This limit is set by the design of the internal metal interconnect. Note that in transient applications, the part is robust.
Power Dissipation
With the high output drive capability of the EL5156 and EL5157 families, it is possible to exceed the 125C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for the application to determine if the load conditions or package types need to be modified for the amplifier to remain in the safe operating area.
Video Performance
For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150, because of the change in output current with DC level. The dG and dP for these families are about 0.006% 11
EL5156, EL5157, EL5256, EL5257
The maximum power dissipation allowed in a package is determined according to:
T JMAX - T AMAX PD MAX = ------------------------------------------- JA
Power Supply Bypassing and Printed Circuit Board Layout
As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as sort as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the VS- pin is connected to the ground plane, a single 4.7F tantalum capacitor in parallel with a 0.1F ceramic capacitor from VS+ to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the VS- pin becomes the negative supply rail. For good AC performance, parasitic capacitance should be kept to minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Minimizing parasitic capacitance at the amplifier's inverting input pin is very important. The feedback resistor should be placed very close to the inverting input pin. Strip line design techniques are recommended for the signal traces.
Where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature JA = Thermal resistance of the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: For sourcing:
n
PD MAX = V S x I SMAX +
i=1
( VS - VOUTi ) x ----------------R Li
n
V OUTi
For sinking:
PD MAX = V S x I SMAX +
( VOUTi - VS ) x ILOADi
i=1
Where: VS = Supply voltage ISMAX = Maximum quiescent supply current VOUT = Maximum output voltage of the application RLOAD = Load resistance tied to ground ILOAD = Load current N = number of amplifiers (Max = 2) By setting the two PDMAX equations equal to each other, we can solve the output current and RLOAD to avoid the device overheat.
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation's quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com 12

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